Digital Signal Processing Reference
In-Depth Information
precoder
F
equalizer
G
q
(
n
)
0
3 /2
1/
c
c
1/ 2
s
(
n
)
0
s
(
n
)
0
1/2
−1/2
1/
2
q
(
n
)
1
H
1/ 2
4
c
4/
c
s
(
n
)
1
s
(
n
)
1
−
1/ 2
3 /2
channel
V
h
U
h
Figure 12.7
. Example 12.2. The precoder and equalizer for the optimal (ZF-
MMSE) transceiver for the channel
H
.
The SVD of this channel is given by
11
1
1 0
0(
/
16)
√
31
1
√
2
1
2
−
1
√
3
H
=
×
×
.
−
1
U
h
Σ
h
V
h
This determines the optimal linear transceiver completely, as shown in Fig.
12.7, except for the constant
c
which is determined from the power con-
straint. More extensive examples will be presented in Chaps. 17 and 18
where we compare several optimal transceivers on the basis of symbol error
probability.
12.5 Optimizing the noise-to-signal ratio
In this chapter we have so far assumed a simple signal covariance matrix
R
ss
=
σ
s
I
and minimized the trace of
R
ee
=
σ
q
GG
†
subject to the power constraint
p
0
=
σ
s
Tr (
FF
†
) and the zero-forcing constraint
GHF
=
I
.If
R
ss
is a more
general diagonal matrix
Λ
s
of the form (12.6) it makes more sense to minimize
the sum of error-to-signal ratios rather than the sum of errors. For, it is the error-
to-signal ratios at the detectors that determine the performance of the receiver.
Thus, it is more appropriate to minimize the trace of the matrix defined as
R
new
=
σ
q
Λ
−
1
/
2
GG
†
Λ
−
1
/
2
s
.
s
With
R
ss
=
Λ
s
the power constraint is modified to
p
0
=
σ
s
Tr (
FΛ
s
F
†
)
.
(12
.
68)
Define
G
1
=
Λ
−
1
/
2
F
1
=
FΛ
1
/
2
G
and
.
(12
.
69)
s
s
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