Wireless Strategies Part 2 (Cooperative Strategies and Rates)

Decode-and-Forward

Decode-and-forward is a block-transmission strategy that has the block structure shown in Figure 4.12 [33, 106]. There are two code books: tmp8-200_thumb[2]The source uses block Markov encoding, i.e., the encoding has one block memory in that the source codeword in block b is tmp8-201_thumb[2]. The idea is that the relay knows wb—1 and decodes wb after having removed the effect oftmp8-202_thumb[2]. The resulting rate bound is

tmp8-206_thumb[2]

The relay can now transmittmp8-207_thumb[2]in block b + 1. The destination decodes wb with a sliding-window decoder that usestmp8-208_thumb[2] (cf. [28, 191, 106]). If the codebooks of every block in Figure 4.12 were chosen independently, the resulting destination rate bound is

tmp8-211_thumb[2]

The term I(X1; Y3 |X2) in (4.31) comes fromtmp8-212_thumb[2](note that the destination already knowstmp8-213_thumb[2]and thustmp8-214_thumb[2]while the term I(X2; Y3) comes fromtmp8-215_thumb[2]is treated as interference).

A DF strategy for a full-duplex relay.

Fig. 4.12 A DF strategy for a full-duplex relay.

 A DF strategy for a full-duplex relay on an AWGN relay channel.

Fig. 4.13 A DF strategy for a full-duplex relay on an AWGN relay channel.

Summarizing, DF achieves the rate

tmp8-222_thumb[2]

The reader might wonder why one can optimize over all joint distributionstmp8-223_thumb[2]One can permit this by constructing the codebooktmp8-224_thumb[2] fromtmp8-225_thumb[2]via superposition coding [32]. To explain this method, consider a full-duplex Gaussian relay channel with the DF block structure shown in Figure 4.13. The idea is that the code booktmp8-226_thumb[2]is constructed by adding (or superposing) codewords from a Gaussian codebooktmp8-227_thumb[2] to codewords from a Gaussian codebooktmp8-228_thumb[2]scaled by The codewords intmp8-229_thumb[2]use power P2. The codewords intmp8-230_thumb[2]use powertmp8-231_thumb[2] wheretmp8-232_thumb[2], and the scaled codewords fromtmp8-233_thumb[2]use powertmp8-234_thumb[2] i.e., we havetmp8-235_thumb[2]Furthermore, the codewordtmp8-236_thumb[2]in block b is independent of the codewordtmp8-237_thumb[2], so the source power constraint is satisfied.

The relay decodes wb at the ratetmp8-238_thumb[2]The destination decodes wb by usingtmp8-239_thumb[2]and its past estimate of tmp8-240_thumb[2]The codewordtmp8-241_thumb[2]is treated as interference. The resulting

DF rate is

tmp8-261_thumb[2]

where we recall thattmp8-262_thumb[2]is the real part of x, and wheretmp8-263_thumb[2] tmp8-264_thumb[2]is the correlation coefficient of the zero-mean X1 and X2, which in this case istmp8-265_thumb[2]Note that, by phase-rotating the relay signal appropriately, the source and relay can coherently combine their signals to give the destination an SNR boost. The price paid is a loss in the information rate from the source to the relay.

We make a few remarks. First, DF differs from classic multi-hop in several important ways:

(1) the source and relay transmit simultaneously

(2) the source and relay signals can be made to coherently combine at the destination if h13 and h23 are known to the transmitter or relay

(3) the destination decodes using several or all of its available output blocks.

These differences remain for half-duplex relays. However, the second difference disappears for fast uniform-phase fading or fast Rayleigh fading, as we shall see. Next, note that the last term in (4.32) is the rate of a point-to-point channel where the transmitter has a vector input [X1 X2]. The DF strategy is thus closely related to multi-antenna transmission. In fact, if the source-to-relay channel capacity is large (say, if the relay is close to the source) then the limiting term in (4.32) is I(X1X2; Y3).

Consider again the case P^N = P2/N = 10, Huv = 1 for all (u,v), a = 2, and the linear geometry of Figure 4.8(b). The resulting DF rates are shown in Figure 4.9 as the curve labeled "DF." The curve labeled "p for DF" shows the optimal correlation coefficient. Observe that DF performs well when the relay is close to the source (d w 0) and even meets the cut-set bound (3.33) when d = 0. Based on Figure 4.9, one would choose DF if the relay is close to the source, and CF if the relay is close to the destination. This insight applies to other networks as well. For example, suppose we have two relays. If both relays are close to the source or the destination, then they should both use DF or CF, respectively. On the other hand, if one relay is close to the source and the other is close to the destination, then the former relay should use DF while the latter should use CF.

CF and DF for Fast Uniform-Phase Fading

Consider the geometry of Figure 4.8(a) and where the Huv are fast fading. As noted in Section 4.2.1, we augment Y2 and Y3 to become [Y2 H12] and [Y3 H13 H23], respectively. From (4.23), the CF rate is thus

tmp8-270_thumb[2]

where

tmp8-271_thumb[2]

and wheretmp8-272_thumb[2]For uniform-phase fading, we havetmp8-273_thumb[2] tmp8-274_thumb[2]and choosetmp8-275_thumb[2]is the same as in Section 4.2.4. The result is that we recover the same rate as in (4.28a)-(4.29) (cf. [106]).

On the other hand, the DF rate is now

tmp8-280_thumb[2]

For the AWGN channel, this rate is

tmp8-281_thumb[2]

where the expectation is over thetmp8-282_thumb[2]that are independent and uniform overtmp8-283_thumb[2]. But Jensen’s inequality gives

tmp8-286_thumb[2]

and we havetmp8-287_thumb[2]The best p in (4.37) is therefore zero [79, 106]. This result is intuitive: without phase knowledge the source and relay cannot coherently combine their signals at the destination. The DF block structure thus simplifies to that shown in Figure 4.14.

A DF strategy for a full-duplex relay and p = 0.

Fig. 4.14 A DF strategy for a full-duplex relay and p = 0.

Rates for a full-duplex relay, uniform-phase fading, Pl/N = P2/N = 10, and a = 2.

Fig. 4.15 Rates for a full-duplex relay, uniform-phase fading, Pl/N = P2/N = 10, and a = 2.

Figure 4.15 plots the CF, DF, and cut-set rates for the linear geometry shown in Figure 4.8(b) and the uniform-phase fading channel with P1/N = P2/N = 10 and a = 2. Perhaps surprisingly, DF achieves capacity when the relay is in a region around the source [106]. Figure 4.16 plots the two-dimensional positions of the relay where DF achieves capacity when P1 = P2. Note that the region grows as a increases. The results in Figures 4.15 and 4.16 generalize to other fast fading channels, e.g., Rayleigh fading channels, and it reinforces the insight from Section 4.2.5 that one should use DF when the relay is near the source. We remind the reader that the distances in

 Positions of the relay where DF achieves capacity with uniform-phase fading and Pi = P2.

Fig. 4.16 Positions of the relay where DF achieves capacity with uniform-phase fading and Pi = P2.

Figures 4.15 and 4.16 should be interpreted as relative distances and not as absolute ones.

Multipath Decode-and-Forward

Multipath decode-and-forward is a variation of DF where the source node first performs rate-splitting, i.e., the message W with rate R is split into W’ and W” having the respective rates R’ and R" such that R’ + R” = R [33, 44, 106]. The same type of rate-splitting is done for multipath routing in Figure 4.3. In fact, MDF generalizes multipath routing from wireline networks to wireless networks. Alternatively, one could say that MDF combines multipath routing and DF.

The MDF block structure is shown in Figure 4.17. The idea is that one replaces X1 in DF with an auxiliary random variable U, i.e., one performs DF with U playing the role of X1. The U represents codewords tmp8-292_thumb[2]that transmit W’, as shown in Figure 4.17. The "path" for W’ can thus be considered to be the entire RC [65]. On the other hand, W” is transmitted by the codewordstmp8-293_thumb[2]that are superposed ontmp8-294_thumb[2]The "path" for W” can thus be considered to be the direct link from the source to the relay.

 An MDF strategy for a full-duplex relay.

Fig. 4.17 An MDF strategy for a full-duplex relay.

Suppose the destination first decodes the messages w[ and then the wf. Based on the above discussion, the rate of MDF is a sum of a DF rate and a point-to-point rate:

tmp8-300_thumb[2]

The MDF superposition method is shown for AWGN channels in Figure 4.18 that generalizes Figure 4.13. The codebooktmp8-301_thumb[2]is constructed by adding codewords from the Gaussian codebookstmp8-302_thumb[2]

tmp8-303_thumb[2]The codewords intmp8-304_thumb[2]use power P2. The code words intmp8-305_thumb[2]have powerstmp8-306_thumb[2]respectively, where

tmp8-307_thumb[2]We must therefore choosetmp8-308_thumb[2] The decoding procedure is as follows. The relay decodestmp8-309_thumb[2]after receivingtmp8-310_thumb[2]The destination decodestmp8-311_thumb[2]after receivingtmp8-312_thumb[2]~ by assuming that its past estimate oftmp8-313_thumb[2]is correct, and by treating tmp8-329_thumb[2]as interference. Finally, the destination removes the effect oftmp8-330_thumb[2]and decodestmp8-331_thumb[2]

An MDF strategy for a full-duplex relay on an AWGN relay channel.

Fig. 4.18 An MDF strategy for a full-duplex relay on an AWGN relay channel.

A mixed wireline/wireless relay channel and its graph.

Fig. 4.19 A mixed wireline/wireless relay channel and its graph.

Unfortunately, for full-duplex AWGN channels the MDF method does not improve the DF method because the optimal choice of PUXiX2 gives either DF or a point-to-point strategy. However, for other AWGN channels the MDF strategy performs better than DF. For example, we shall later see that MDF improves on DF for half-duplex channels. MDF even achieves capacity for an important class of channels discussed next.

Suppose we have the mixed network shown in Figure 4.19 where the source-to-relay channel is a wireline channel. We model this by using X1 = [X12 X13] and the channel

tmp8-335_thumb[2]

where we permit X2 to contribute to Y2, i.e., the channel (4.41) includes port constraints such as (3.1). For the MDF rate (4.40), we choose U = X12 and

tmp8-336_thumb[2]

We compute

tmp8-337_thumb[2]

where the maximization is over all distributions of the form (4.42). One can check that the cut-set bound (3.33) also gives (4.43) because the best input distributions factor as (4.42). The MDF rate (4.43) is therefore the capacity of the mixed relay channel [47].

We remark that this channel also models cases where nodes 1 and 2 are wireless and the source-to-relay channel is "orthogonal" to the destination channel. For example, this happens if the source-to-relay channel uses a different frequency band than the destination channel.

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