Global Positioning System Reference
In-Depth Information
1
Q
=
=
15
.
(6.15)
∞
∫
(
)
2
4
RT
sinc
π
fT f
c
c
c
−∞
4.5,
depending upon the subcarrier frequency, the spreading code rate, and whether
cosine-phasing or sine-phasing is used.
For a BOC(
m
,
n
) modulation,
Q
takes on values in the range 3
≤
Q
≤
Case 3—Bandlimited White Noise Interference.
When the interference has flat
spectrum centered at
f
and extending from
f
−
/2
≤
f
≤
f
+
/2, its spectrum is
expressed as
1
,
f
−
β
2
≤
f
≤
f
+
β
2
()
Sf
=
ι
ι
ι
ι
(6.16)
β
ι
ι
0
,
elsewhere.
Substituting (6.16) into (6.12) yields
1
Q
=
(6.17)
f
+
β
2
R
ι
ι
()
∫
c
Sf f
S
β
ι
f
−
β
2
ι
ι
β
ι
becomes small, (6.17) approaches (6.13), the result for narrowband inter-
ference.
If
If
β
ι
is large enough so that almost all of the signal power is included within
f
−
/2
≤
f
≤
f
+
/2, then (6.17) becomes
β
ι
Q
=
(6.18)
R
c
Rearranging (6.18),
QR
c
= β
ι
, which shows that modulation design, and in par-
ticular higher spreading code rates, provide no benefit to (
C
S
/
N
0
)
eff
when the noise
spectrum is flat over the frequency range occupied by the signal. Moreover, for fixed
interference power, the wider the interference bandwidth, the larger the value of
Q
,
and hence the smaller influence of the interference on (
C
S
/
N
0
)
eff
.
When the signal is BPSK-R(
n
) and the interference spectrum is centered on the
signal spectrum so that
f
ι
=
0, substituting (4.14) into (6.17) yields
1
Q
=
(6.19)
β
2
1
ι
(
)
∫
sinc
2
π
fT
df
c
β
ι
β
2
ι
2
R
c
so that the interference covers the null-to-null main
lobe of the signal spectrum, (6.19) becomes
When in addition
β
ι
=
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