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measures how well the time-domain signal
x
(
t
) can be approximated by counterclock-
wise rotating phasors. Similarly, the magnitude of the CR-TFD, normalized by the
time- and frequency-marginals of the HR-TFD, measures how well the time-domain
signal
x
(
t
) can be approximated by clockwise rotating phasors. This suggests that the
distribution of coherence (rather than energy or power) over time and frequency is a
fundamental descriptor of a nonstationary signal.
Finally we point out that, if
x
(
t
) is WSS, the estimator
x
f
(
t
) simplifies to
(
f
)e
j2
π
ft
x
f
(
t
)
=
d
ξ
(9.98)
for all
t
, which has already been shown in Section
8.4.2
. Furthermore, since WSS
analytic signals are proper, the conjugate-linear estimator is identically zero:
x
f
(
t
)
0
for all
t
. Hence, WSS analytic signals can be estimated only from counterclockwise
rotating phasors, whereas nonstationary improper analytic signals may also be estimated
from clockwise rotating phasors.
=
9.3.2
Kernel estimators
The Rihaczek distribution is a mathematical expectation. As a practical matter, it must
be estimated. Because such an estimator is likely to be implemented digitally, we present
it for a time series
x
[
k
]. We require that our estimator be a bilinear function of
x
[
k
] that
is covariant with respect to shifts in time and frequency. Estimators that satisfy these
properties constitute Cohen's class.
10
(Since we want to perform time- and frequency-
smoothing, we do not expect our estimator to have the correct time- and frequency-
marginals.) The discrete-time version of Cohen's class is
V
xx
[
k
]
x
∗
[
k
m
]e
−
j
µθ
,
,θ
)
=
x
[
k
+
m
+
µ
]
φ
[
m
,µ
+
(9.99)
m
µ
where
m
is a global and
µ
a local time variable. The choice of the dual-time kernel
] determines the properties of the HR-TFD estimator
V
xx
[
k
φ
). Omitting the
conjugation in (
9.99
) gives an estimator of the CR-TFD. It is our objective to design
a suitable kernel
[
m
,µ
,θ
φ
[
m
,µ
]. A factored kernel that preserves the spirit of the Rihaczek
distribution is
w
3
[
m
]
φ
[
m
,µ
]
=
w
1
[
m
+
µ
]
w
2
[
µ
]
.
(9.100)
In practice, the three windows
w
1
,
w
2
, and
w
3
might be chosen real and even. By
inserting (
9.100
)into(
9.99
), we obtain
m
]
π
−
π
m
w
3
[
m
]
x
∗
[
k
)e
j
m
(
θ
−
ω
)
d
ω
V
xx
[
k
,θ
)
=
+
W
2
(
ω
)
F
1
[
k
,θ
−
ω
π
.
(9.101)
2
Here
W
2
(
ω
) is the discrete-time Fourier transform (DTFT) of
w
2
[
µ
] and
F
1
is the
short-time Fourier transform (STFT) of
x
[
k
] using window
w
1
, defined as
n
w
1
[
n
]
x
[
n
k
]e
−
j
n
θ
.
F
1
[
k
,θ
)
=
+
(9.102)
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