Digital Signal Processing Reference
In-Depth Information
filters. However, as mentioned earlier, they can also be used in time-domain
analysis, particularly when the
z
-transform technique cannot be used. To illustrate
this point, we provide the following examples.
Let the unit impulse response of a discrete-time system be given as
h(n)
=
(
0
.
2
)
n
u(n)
and the input sequence be given as
x(n)
(
0
.
5
)
−
n
u(
=
−
n)
. Therefore
e
jω
e
jω
1
1
−
0
.
2
e
−
jω
=
H(e
jω
)
=
−
0
.
2
e
−
jω
e
−
jω
1
X(e
jω
)
=
0
.
5
e
jω
=
1
−
−
0
.
5
e
jω
e
jω
e
−
jω
e
−
jω
Y(e
jω
)
H(e
jω
)X(e
jω
)
=
=
−
0
.
2
−
0
.
5
Now let
k
1
e
jω
e
jω
k
2
e
−
jω
e
−
jω
Y(e
jω
)
=
−
0
.
2
+
−
0
.
5
so that we can easily obtain the inverse DTFT of each term. Note the difference
in the two terms.
Then we compute
k
1
from the following method, which is slightly different
from the partial fraction method we have used earlier:
e
−
jω
e
−
jω
k
2
(e
jω
−
0
.
2
)
Y(e
jω
)e
−
jω
(e
jω
−
0
.
5
)
e
−
j
2
ω
−
0
.
2
)
=
=
k
1
+
(e
−
jω
−
0
.
5
Evaluating both terms at
e
jω
=
0
.
2 yields
e
jω
=
0
.
2
=
e
−
jω
e
−
jω
5
4
.
5
=
1
.
111
k
1
=
−
0
.
5
Similarly, the constant
k
2
is evaluated as follows (again, this is slightly different
from the partial fraction expansion method we have used earlier):
e
jω
e
jω
k
1
e
j
2
ω
(e
−
jω
−
0
.
5
)
Y(e
jω
)e
jω
(e
−
jω
−
0
.
5
)
=
+
k
2
=
e
jω
−
0
.
2
−
0
.
2
Evaluating the two terms at
e
jω
2
1
.
8
=
2
.
0 yields
k
2
=
=
1
.
111. Therefore we
have
Y(e
jω
)
=
1
.
111
e
jω
/(e
jω
+
1
.
111
e
−
jω
/(e
−
jω
−
0
.
2
)
−
0
.
5
)
, and the output
=
1
.
111
(
0
.
2
)
n
u(n)
+
1
.
111
(
0
.
5
)
−
n
u(
is
y(n)
n)
.
Now we describe a preferred method of finding the inverse DTFT of
−
e
jω
e
jω
e
−
jω
e
−
jω
Y(e
jω
)
H(e
jω
)X(e
jω
)
=
=
−
0
.
2
−
0
.
5
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