Digital Signal Processing Reference
In-Depth Information
where
−
1
≤ α
1,1
<
1 and 0
≤ β
1,1
≤
1. We immediately find that the unique
solution to (3.34) is
1
− β
1,1
e
ωτ
1
−
(1
− β
1,1
)
e
1
1
− e
ωτ
0
(1
− α
1,1
)
h
(
ω
)=
,
(3.35)
−
ωτ
2
where
τ
1
=
τ
0
(1
− α
1,1
) and
τ
2
=
τ
0
α
1,1
. Approximating 1
−e
ωτ
0
(1
− α
1,1
)
with (3.6), we get
1
− β
1,1
e
ωτ
1
−
(1
− β
1,1
)
e
C
1
− α
1,1
·
1
ω
h
(
ω
)
≈
,
(3.36)
−
ωτ
2
from which we deduce the equivalent filter
1
:
1
− β
1,1
e
ωτ
1
−
(1
− β
1,1
)
e
(
ω
)=
1
ω
′
h
.
(3.37)
−
ωτ
2
′
Taking the complex conjugate of the components of
h
(
ω
), we get the gains
that should be applied at the two microphone outputs:
−
ωτ
1
1
(
ω
)=
1
− β
1,1
e
H
′∗
,
(3.38)
ω
2
(
ω
)=
−
(1
− β
1,1
)
e
ωτ
2
ω
′∗
H
,
(3.39)
−
ωτ
1
and
e
ωτ
2
are time-domain delays
τ
1
and
−τ
2
at the
first and second microphone outputs, respectively. Figure 3.11 illustrates the
implementation of the first-order differential array.
The beampattern corresponding to the beamformer
h
where the term
e
′
(
ω
) is
1
− β
1,1
e
ωτ
1
−
(1
− β
1,1
)
e
ω
(
τ
0
cos
θ − τ
2
)
(
ω
)
,θ
]=
1
ω
′
B
[
h
(3.40)
and applying the approximation (3.6) to the previous expression leads to
(
ω
)
,θ
]
≈
1
− α
1,1
C
1
−
1
− β
1,1
1
− α
1,1
+
1
− β
1,1
′
B
[
h
1
− α
1,1
cos
θ
,
(3.41)
which is recognized to be the pattern of the first-order DMA. There are five
interesting cases.
•
Dipole:
α
1,1
=
β
1,1
= 0 (see Section 3.2).
•
Cardioid:
α
1,1
=
−
1
,β
1,1
= 0 (see Section 3.3).
•
Subcardioid [2], [3]:
α
1,1
=
−
1
,β
1,1
=0
.
4.
Hypercardioid:
α
1,1
=
−
2
,β
1,1
= 0.
•
1
Notice that this filter is noncausal for
Α
1,1
>
0. In this case, we need to add a processing
delay equal to
Τ
0
Α
1,1
=
Τ
2
.
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