Digital Signal Processing Reference
In-Depth Information
3.3 First-Order Cardioid
◦
In the first-order cardioid, there is a one at the angle 0
and a null at the
◦
angle 180
(i.e.,
α
1,1
=
−
1). Therefore, our linear system of two equations is
1
e
ωτ
0
1
e
1
0
h
(
ω
)=
.
(3.19)
−
ωτ
0
We easily find that the solution is
1
1
− e
2
ωτ
0
1
−e
ωτ
0
h
(
ω
)=
.
(3.20)
Using (3.6) to approximate 1
− e
2ωτ
0
, we obtain
h
(
ω
)
≈
1
2
ωτ
0
1
−e
ωτ
0
,
(3.21)
from which we deduce the equivalent filter:
(
ω
)=
1
ω
1
−e
ωτ
0
′
h
,
(3.22)
2
=
2τ
0
is a constant across frequencies. Taking the complex conjugate
of the components of
h
C
since
′
(
ω
), we get the gains that should be applied at the
two microphone outputs:
1
(
ω
)=
1
′∗
H
ω
,
(3.23)
2
(
ω
)=
−
1
−
ωτ
0
,
′∗
H
ω
e
(3.24)
−
ωτ
0
is simply a time-domain delay
τ
0
at the second mi-
crophone output. Figure 3.6 illustrates the implementation of the first-order
cardioid.
The beampattern of the beamformer
h
where the term
e
′
(
ω
) is
(
ω
)
,θ
]=
1
ω
1
− e
ωτ
0
(1+cos
θ
)
′
B
[
h
.
(3.25)
Figure 3.7 displays the patterns from (3.25) for several frequencies and two
values of
δ
. Applying the approximation (3.6) to (3.25) leads to
(
ω
)
,θ
]
≈
C
1
2
+
1
′
B
[
h
2
cos
θ
,
(3.26)
which is the pattern of the first-order cardioid.
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